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论文研究-Blind Beamforming for Noncircular Signals.pdf
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非圆信号盲波束形成,徐友根,刘志文,Blind beamforming for extracting noncircular signals without a prior knowledge on the desired steering vector is considered in this paper. Three second-order statistic based blind
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- 1 -
Abstract
Blind beamforming for extracting noncircular signals without a prior knowledge on the desired steering vector is
considered in this paper. Three second-order statistic based blind schemes, termed as subspace decomposition,
self-reference, and extraction power maximization methods, respectively, are proposed to extract one desired non-
circular signal from a number of statistically independent circular interferences in the presence of circular Gaus-
sian noise with arbitrary and unknown correlation structure. Two joint second- and fourth-order cumulant based
methods are also developed for the case of multiple noncircular interferences. One is ESPRIT (estimation of signal
parameters via rotational invariance techniques) type method. The other represents a real-valued extension of the
WL-MVDR (widely linear minimum variance distortionless response). Numerical examples are shown to illustrate
the performance of the proposed methods. The latest version of this online-only showing has also been submitted
to IET Signal Processing.
Keywords: Array signal processing, adaptive arrays, noncircular signals, blind beamforming
1. Introduction
Blind beamforming has found numerous important applications in radar, sonar, wireless communi-
cations, and biomedical imaging, mainly because it can restore one or more desired signals from multi-
ple cochannel interfering signals and noise without a prior knowledge of the array manifold and the
need for training signal [1-2]. In contrast, the non-blind beamforming techniques, such as MVDR
(minimum variance distortionless response [3]) and LCMV (linear constrained minimum variance [3]),
require the information about the steering vector of the signal-of-interest (SOI), thereby necessitating
an array calibration procedure. However, the advance calibration of the array characteristics is usually
expensive and may become uncertain especially in the presence of multipath propagation and environ-
mental changes.
The very earlier attempt for blind beamforming seems to be achieved by assuming structural proper-
ties of the array manifold. In such methods, the direction-of-arrival (DOA) of the desired signal is first
estimated by using direction finding techniques such as MUSIC (multiple signal classification [4]) and
ESPRIT (estimation of signal parameters via rotational invariance techniques [5]). The DOA estimate
then can be used to construct the desired steering vector, after which a certain beamformer can be de-
signed to extract the signal from that direction. Strictly speaking, this two-step method is not a truly
“blind” method since it requires also array calibration. More importantly, DOA estimation may be
complex and inadequate when the array is sensitive to both DOA and signal polarization, or, very fre-
quently, suffers from severe element mutual coupling. Later, new types of blind beamformers were
proposed that are not based on the receiving channel structure, but instead exploit the structural char-
acters of the signal waveform. A promising example is the constant modulus algorithm (CMA) that can
extract signals with constant amplitude (such as phase modulated signals) [6-7]. However, CMA is
very sensitive to the initialization condition, and generally poorly convergent. An analytical CMA
variant provided later in [8] was observed to be able to avoid such convergence problems.
The cyclostationarity property of many man-made communication signals can also be exploited for
blind beamforming by processing the incoming signals at the carrier frequency (i.e., without demodula-
tion). A popular cyclostationarity-exploiting blind method labeled as SCORE (spectral self-coherence
restoral [9]) can extract the signal at a known (or can be estimated to alleviate the effect of cycle fre-
quency perturbation caused by channel uncertainty such as Doppler shift [10]) cycle frequency auto-
matically. Some other interesting cyclostationarity resorted blind beamformers can be found in [11-13]
(and references therein). In the literature, there are still some efforts made on the exploitation of the
temporal correlation structure of the colored or nonstationary signals, see, for example, [14-15] and
references therein. A fundamental and necessary requirement of the algorithms there is that the incom-
This work was supported by the National Natural Science Foundation of China under Grant 60602037.
Blind Beamforming for Noncircular Signals
Yougen Xu, and Zhiwen Liu
Department of Electronic Engineering, Beijing Institute of Technology, Beijing 100081, China
E-mail: yougenxu@bit.edu.cn
http://www.paper.edu.cn
- 2 -
ing signals have distinct power spectral densities (PSDs).
Note that all the aforementioned property-restoral type blind beamformers can be accomplished by
using second-order statistics (SOS) alone (based on the fact that the desired signal and the interferences
are temporally separable). For the more general case of arbitrary non-Gaussian signals, a variety of
blind methods based on the higher-order statistics (HOS) have been proposed [16-22] (and references
therein). A striking example is JADE (joint approximate diagonalization of eigen-matrices [16]),
wherein second-order statistics are used to whiten the signal contribution of the received noisy data
prior to cumulant based diagonalization (iterative). A major drawback of JADE is the requirement of
the knowledge about noise covariance matrix. Still, it is assumed by JADE that all the incident signals
are non-Gaussian and have nonzero and unequal kurtoses. A natural cure for these shortcomings is to
whiten the signal via the HOS instead, as has done in [19-20]. Also, a closed-form cumulant based
blind beamformer was proposed in [17] to recover a single non-Gaussian signal from multiple Gaus-
sian interferences, while an ESPRIT-type method was suggested in [21] to avoid whitening step. Some
other work on cumulant based blind beamforming can be found in [22-23] and references therein.
More recently, a few efforts have been made on the exploitation of noncircularity of signals such as
amplitude modulated (AM) signal and binary phase-shift keying (BPSK) signal. For example, the Ta-
kagi factorizing technique was used in [24-25], based on SOS only. However, algorithms there require
that the signals to be separated have distinct noncircularity rates — a condition violated by many non-
circular signals encountered in communications (such as rectilinear signals). Also, JADE and ICA (in-
dependent component analysis) have been extended for noncircular signal blind beamforming in [23-24]
and [26-27], respectively. Still, some interesting work on DOA estimation of noncircular signals can be
found in [28-30] (and references therein). In this paper, we limit ourselves also to blind beamforming
for noncircular signals. We propose three SOS based blind methods for the case of one noncircular SOI
corrupted by a number of circular interferences. We further provide a new mixed-order blind algorithm
for the case where both the desired signal and interfering signals are noncircular. We still extend a re-
cently developed noncircularity-exploiting MVDR beamformer [31] to a real-valued form in a blind
situation.
The paper is organized as follows. In Section II, we formulate the problem. In Section III, we present
three methods for blind beamforming in the presence of circular interferences. In Section IV, we pro-
pose two mixed-order blind methods for the case of noncircular interferences. We then provide several
numerical examples in Section V and finally conclude the paper in Section VI. Throughout the paper,
we use uppercase and lowercase boldface letters to denote vectors and matrices, respectively. Symbols
“
∗ ”, “
T
”, and “
H
” represent complex conjugate, transpose, and complex conjugate transpose, re-
spectively. Furthermore, “
E ” and “cum ” signify statistical expectation and the fourth-order cumulant,
respectively.
2. Problem Formulation
A complex signal ()st is said to be noncircular (at order 2) if
2
0{()}Es t ≠ . In other words, a
noncircular signal has nonvanishing conjugate correlation as well as nonzero correlation (that is,
22
{| ( ) | }
s
Estσ =
). Generally,
22
{()}
j
s
Es t e
ϖ
σ= =
, where
= is referred to as the noncircularity rate.
Note that
01≤≤= [29]. For example, a BPSK signal has a noncircularity rata of 1 (completely non-
circular signal). Typical examples of noncircular signal include AM, BPSK, amplitude phase-shift
keying (ASK), minimum shift keying (MSK), etc [28, 29].
Consider an array of
N elements, with arbitrary unknown response patterns and locations. Assume
that there are
Q interfering signals 1{ ( ), ,..., }
i
j
st j Q= , and a noncircular desired signal, ()
d
st, im-
pinging upon the array. Further, the additive noise (either white or colored) present is assumed to be
circular with unknown covariance. With these basic assumptions, the received baseband signal at the
k-th sensor can be modeled as
1
() ( ) () ( ) () ()
Q
dd ii
kk kjjk
j
xt a st a st nt
=
=+ +
∑
θθ (1)
where
d
θ
and
i
j
θ
are the parameter vector (contains DOA and polarization etc.) of the desired signal
and the
j-th interfering signal, respectively; ()
k
a θ is the response of the k-th sensor to the signal
wave-front with parameter vector
θ ; ()
k
nt is the additive noise at the k-th sensor. It is assumed that
http://www.paper.edu.cn
- 3 -
the desired signal and the interfering signals are statistically independent, and all the signals are statis-
tically independent of the noise. Note that the model (1) applies also to the case of multipath propaga-
tion and smart jamming. Furthermore, it can be rewritten in matrix notation, as
def
def
12
1
2
1
1
()
() () () ()
()
()
()
()
() () ()
()
()
T
N
d
i
di i
Q
i
N
Q
t
txtxt xt
st
nt
nt
st
nt
st
=
=
⎡⎤
=
⎢⎥
⎣⎦
⎛⎞
⎛⎞
⎟
⎜
⎟
⎜
⎟
⎜⎟
⎜
⎟
⎟
⎜
⎜
⎟
⎟
⎜
⎜
⎟
⎟
⎜
⎟
⎜
⎟
⎜
⎟
⎡⎤
⎜
⎟
⎟
⎜
=+
⎟
⎜
⎟
⎢⎥
⎜
⎟
⎜
⎣⎦
⎟
⎜
⎟
⎜
⎟
⎟
⎜
⎜
⎟
⎟
⎜
⎜
⎟
⎟
⎜
⎟
⎜
⎟
⎜
⎟
⎜
⎟
⎜
⎟
⎜
⎝⎠
⎝⎠
A
s
x
aa a
"
"
#
#
θθ θ
()
( ) () () ()
() ()
t
dd ii
st t t
tt
=++
=+
n
aAsn
As n
θ
(2)
where
1
( ) [ ( ),..., ( )]
T
N
aa=a θθ θ is the generalized response vector,
1
[ ( ),..., ( )]
ii i
Q
=Aa aθθ, =A
[( ), ]
di
aAθ ,
1
( ) [ ( ),..., ( )]
ii iT
Q
tstst=s . In what follows, we assume that A has full column rank, and
the noise is circular and Gaussian, that is,
{() ()}
{() ()}
H
nN
T
N
n
Et t
Et t
∗
= ≠
==
Rnn O
Rnn O
where “
N
O ” denotes an NN× zero matrix, and
n
R ,
n
∗
R are called the noise covariance matrix
and the noise conjugate covariance matrix, respectively.
The optimum beamforming weight vector for a so-called “informed [16]” beamformer is given by
1
opt
()
d
x
μ
−
=wRaθ , where μ is a scalar for maintaining a specified response for the desired signal,
and
x
R is the array covariance matrix, defined as
{() ()}
HH
xsn
Et t==+Rxx ARAR (3)
where {() ()}
H
s
Et t=Rss is the source covariance matrix.
We address here the problem of optimum beamforming with an array of arbitrary sensors whose re-
sponses and locations are completely unknown (without any
a prior knowledge about the steering vec-
tor(s) of the desired signal(s)), aiming at extracting the noncircular desired signal(s) from the circular
noise plus a number of circular or noncircular interferences.
3. Circular Interference Case
In this section, we present three approaches for estimating the steering vector (instead of DOA) of
the desired signal by exploiting the conjugate cumulant redundancy. These approaches make it possible
for the signal-selection applications where a few noncircular SOIs must be separated from very dense
interference environments.
A. Subspace decomposition (SD) method
The second-order conjugate covariance matrix (also termed as “improper- [32]”, “elliptic- [28]” or
“pseudo- [27]” covariance matrix), is defined as
{() ()}
{ ( )[ ( )] }( ) { ( )[ ( )] }
()()
()()
T
x
ii iT iT T
ddTd
ddTd T
s
Et t
Et t Ett
ρ
ρ
∗
∗
=
=+
+
==
Rxx
As s A nn
aa
aa ARA
θθ
θθ
(4)
where
2
0{[ ( )] }
dd
Estρ = ≠ , diag 0 0{ ( ) ( )} ( , ,..., )
Td
s
Et t ρ
∗
==Rss . The conjugate covariance ma-
trix
x
∗
R has the following singular value decomposition (SVD):
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